NCP1653(A) Datasheet by ON Semiconductor

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© Semiconductor Components Industries, LLC, 2015
May, 2015 − Rev. 10
1Publication Order Number:
NCP1653/D
NCP1653, NCP1653A
Compact, Fixed-Frequency,
Continuous Conduction
Mode PFC Controller
The NCP1653 is a controller designed for Continuous Conduction
Mode (CCM) Power Factor Correction (PFC) boost circuits. It
operates in the follower boost or constant output voltage in 67 or 100
kHz fixed switching frequency. Follower boost offers the benefits of
reduction of output voltage and hence reduction in the size and cost
of the inductor and power switch. Housed in a DIP−8 or SO−8
package, the circuit minimizes the number of external components
and drastically simplifies the CCM PFC implementation. It also
integrates high safety protection features. The NCP1653 is a driver
for robust and compact PFC stages.
Features
•IEC1000−3−2 Compliant
•Continuous Conduction Mode
•Average Current−Mode or Peak Current−Mode Operation
•Constant Output Voltage or Follower Boost Operation
•Very Few External Components
•Fixed Switching Frequency: 67 kHz = NCP1653A,
Fixed Switching Frequency: 100 kHz = NCP1653
•Soft−Start Capability
•VCC Undervoltage Lockout with Hysteresis (8.7 / 13.25 V)
•Overvoltage Protection (107% of Nominal Output Level)
•Undervoltage Protection or Shutdown (8% of Nominal Output Level)
•Programmable Overcurrent Protection
•Programmable Overpower Limitation
•Thermal Shutdown with Hysteresis (120 / 150_C)
•This is a Pb−Free Device
Typical Applications
•TV & Monitors
•PC Desktop SMPS
•AC Adapters SMPS
•White Goods
AC
Input
EMI
Filter Output
In Gnd
Vcontrol Drv
FB VCC
CS VM
15 V
NCP1653
Figure 1. Typical Application Circuit
PDIP−8
P SUFFIX
CASE 626
1
8
PIN CONNECTIONS
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MARKING DIAGRAMS
SO−8
D SUFFIX
CASE 751
1
FB 8VCC
2
Vcontrol
3
In
4
CS
7Drv
6GND
5VM
(Top View)
A suffix = 67 kHz option
A = Assembly Location
WL, L = Wafer Lot
YY, Y = Year
WW, W = Work Week
G or G= Pb−Free Package
1
8
1
8
NCP1653
AWL
YYWWG
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N1653
ALYW
G
1
8
1
8
NCP1653A
AWL
YYWWG
1653A
ALYW
G
1
8
See detailed ordering and shipping information on page 19 of
this data sheet.
ORDERING INFORMATION
— Ivvx H 0 AC EMI _ _. __ Inpui FIHer r‘ 0m 3 A CM RC5 on :4 r7 0“ IFE Current Vmg Mirror 96% w my IFB Regmanon Biock Overvoimge UVLO Protecnon — 11 “FE > 107% he» i | | | = | | Vcc : Reference mock Turn on | i f Iniemai Bias - RM'S'va: 2| Thermai snumown 1120 / 150 CC) Overcuvrent Proiechon ‘— PFC (l5 > 200 M) Modulation R Q {l—r S Figure 2. Functional Block Diagram
NCP1653, NCP1653A
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Figure 2. Functional Block Diagram
0 1
300 k
−
+
+
−
OR
1
8
4
5
2
3
7
6
9 V
0 1 1 0
x
+
9 V
AC
Input
EMI
Filter Cfilter
RCS
Cbulk
off
on
RFB
Output Voltage (Vout)
L
IFB
Current
Mirror
Overvoltage
Protection
(IFB > 107% Iref)
Thermal
Shutdown
(120 / 150 °C)
Current
Mirror
FB
ref
reg
V
II
96%
Regulation Block
ref
I
VCC
Internal Bias
Reference Block
18 V
VCC
VCC UVLO
FB / SD 9 V
Current
Mirror
VCC
Output
Driver
S
RQ
PFC
Modulation
Cramp
Gnd
Ccontrol
Vcontrol
9 V
Overcurrent
Protection
(IS > 200 mA)
IL
IL
Vin
Iin
VM
IM
13.25 V
/ 8.7 V
Turn on
Rvac
Ivac
Cvac
In
12 k
9 V
CMRMIS
RS
CS
Drv
67 or 100 kHz clock
Vramp
Vref
Ich
Shutdown / UVP
(IFB < 8% Iref)
4% Iref Hysteresis
Overpower
Limitation
(IS Ivac > 3 nA2)
Icontrol = Vcontrol
R1
VM = RMISIvac
2 Icontrol
&
R1 = constant
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PIN FUNCTION DESCRIPTION
Pin Symbol Name Function
1FB / SD Feedback /
Shutdown
This pin receives a feedback current IFB which is proportional to the PFC circuit output voltage.
The current is for output regulation, output overvoltage protection (OVP), and output undervoltage
protection (UVP).
When IFB goes above 107% Iref, OVP is activated and the Drive Output is disabled.
When IFB goes below 8% Iref, the device enters a low−consumption shutdown mode.
2 Vcontrol Control Voltage /
Soft−Start
The voltage of this pin Vcontrol directly controls the input impedance and hence the power factor of
the circuit. This pin is connected to an external capacitor Ccontrol to limit the Vcontrol bandwidth
typically below 20 Hz to achieve near unity power factor.
The device provides no output when Vcontrol = 0 V. Hence, Ccontrol also works as a soft−start
capacitor.
3 In Input Voltage
Sense
This pin sinks an input−voltage current Ivac which is proportional to the RMS input voltage Vac.
The current Ivac is for overpower limitation (OPL) and PFC duty cycle modulation. When the
product (IS⋅Ivac) goes above 3 nA2, OPL is activated and the Drive Output duty ratio is reduced by
pulling down Vcontrol indirectly to reduce the input power.
4 CS Input Current
Sense
This pin sources a current IS which is proportional to the inductor current IL. The sense current IS
is for overcurrent protection (OCP), overpower limitation (OPL) and PFC duty cycle modulation.
When IS goes above 200 mA, OCP is activated and the Drive Output is disabled.
5 VMMultiplier
Voltage
This pin provides a voltage VM for the PFC duty cycle modulation. The input impedance of the
PFC circuit is proportional to the resistor RM externally connected to this pin. The device operates
in average current−mode if an external capacitor CM is connected to the pin. Otherwise, it
operates in peak current−mode.
6 GND The IC Ground −
7 Drv Drive Output This pin provides an output to an external MOSFET.
8 VCC Supply Voltage This pin is the positive supply of the device. The operating range is between 8.75 V and 18 V with
UVLO start threshold 13.25 V.
MAXIMUM RATINGS
Rating Symbol Value Unit
FB, Vcontrol, In, CS, VM Pins (Pins 1−5)
Maximum Voltage Range
Maximum Current
Vmax
Imax
−0.3 to +9
100
V
mA
Drive Output (Pin 7)
Maximum Voltage Range
Maximum Current Range (Note 3)
Vmax
Imax
−0.3 to +18
1.5
V
A
Power Supply Voltage (Pin 8)
Maximum Voltage Range
Maximum Current
Vmax
Imax
−0.3 to +18
100
V
mA
Transient Power Supply Voltage, Duration < 10 ms, IVCC < 20 mA 25 V
Power Dissipation and Thermal Characteristics
P suffix, Plastic Package, Case 626
Maximum Power Dissipation @ TA = 70°C
Thermal Resistance Junction−to−Air
D suffix, Plastic Package, Case 751
Maximum Power Dissipation @ TA = 70°C
Thermal Resistance Junction−to−Air
PD
RqJA
PD
RqJA
800
100
450
178
mW
°C/W
mW
°C/W
Operating Junction Temperature Range TJ−40 to +125 °C
Storage Temperature Range Tstg −65 to +150 °C
Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality
should not be assumed, damage may occur and reliability may be affected.
1. This device series contains ESD protection and exceeds the following tests:
Pins 1−8: Human Body Model 2000 V per JEDEC Standard JESD22, Method A114.
Machine Model Method 190 V per JEDEC Standard JES222, Method A115A.
2. This device contains Latchup protection and exceeds ±100 mA per JEDEC Standard JESD78.
3. Guaranteed by design.
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ELECTRICAL CHARACTERISTICS (For typical values TJ = 25°C. For min/max values, TJ = −40°C to +125°C, VCC = 15 V,
IFB = 100 mA, Ivac = 30 mA, IS = 0 mA, unless otherwise specified)
Characteristics Pin Symbol Min Typ Max Unit
OSCILLATOR
Switching Frequency NCP1653
NCP1653A
7 fSW 90
60.3
102
67
110
73.7
kHz
Maximum Duty Cycle (VM = 0 V) (Note 3) 7 Dmax 94 − − %
GATE DRIVE
Gate Drive Resistor
Output High and Draw 100 mA out of Drv pin (Isource = 100 mA)
Output Low and Insert 100 mA into Drv pin (Isink = 100 mA)
7
ROH
ROL
5.0
2.0
9.0
6.6
20
18
W
W
Gate Drive Rise Time from 1.5 V to 13.5 V (Drv = 2.2 nF to Gnd) 7 tr−88 −ns
Gate Drive Fall Time from 13.5 V to 1.5 V (Drv = 2.2 nF to Gnd) 7 tf−61.5 −ns
FEEDBACK / OVERVOLTAGE PROTECTION / UNDERVOLTAGE PROTECTION
Reference Current (VM = 3 V) 1 Iref 192 204 208 mA
Regulation Block Ratio 1 IregL/Iref 95 96 98 %
Vcontrol Pin Internal Resistor 2 Rcontrol −300 −kW
Maximum Control Voltage (IFB = 100 mA) 2 Vcontrol(max) −2.4 −V
Maximum Control Current (Icontrol(max) = Iref / 2) 2 Icontrol(max) −100 −mA
Feedback Pin Voltage (IFB = 100 mA)
Feedback Pin Voltage (IFB = 200 mA)
1 VFB1 1.0
1.3
1.5
1.8
1.9
2.2
V
V
Overvoltage Protection
OVP Ratio
Current Threshold
Propagation Delay
1
IOVP/Iref
IOVP
tOVP
104
−
−
107
214
500
−
230
−
%
mA
ns
Undervoltage Protection (VM = 3 V)
UVP Activate Threshold Ratio
UVP Deactivate Threshold Ratio
UVP Lockout Hysteresis
Propagation Delay
1
IUVP(on)/Iref
IUVP(off)/Iref
IUVP(H)
tUVP
4.0
7.0
4.0
−
8.0
12
8.0
500
15
20
−
−
%
%
mA
ns
CURRENT SENSE
Current Sense Pin Offset Voltage (IS = 100 mA) 4 VS0 10 30 mV
Overcurrent Protection Threshold (VM = 1 V) 4 IS(OCP) 185 200 215 mA
OVERPOWER LIMITATION
Input Voltage Sense Pin Internal Resistor 4 Rvac(int) −12 −kW
Over Power Limitation Threshold 3−4 IS × Ivac −3.0 −nA2
Sense Current Threshold (Ivac = 30 mA, VM = 3 V)
Sense Current Threshold (Ivac = 100 mA, VM = 3 V)
4 IS(OPL1)
IS(OPL2)
80
24
100
32
140
48
mA
mA
CURRENT MODULATION
PWM Comparator Reference Voltage 5 Vref 2.25 2.62 2.75 V
Multiplier Current (Vcontrol = Vcontrol(max), Ivac = 30 mA, IS = 25 mA)
Multiplier Current (Vcontrol = Vcontrol(max), Ivac = 30 mA, IS = 75 mA)
Multiplier Current (Vcontrol = Vcontrol(max) / 10, Ivac = 30 mA, IS = 25 mA)
Multiplier Current (Vcontrol = Vcontrol(max) / 10, Ivac = 30 mA, IS = 75 mA)
5 IM1
IM2
IM3
IM4
1.0
3.2
10
30
2.85
9.5
35
103.5
5.8
18
58
180
mA
mA
mA
mA
THERMAL SHUTDOWN
Thermal Shutdown Threshold (Note 4) −TSD 150 − − °C
Thermal Shutdown Hysteresis − − − 30 −°C
4. Guaranteed by design.
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ELECTRICAL CHARACTERISTICS (For typical values TJ = 25°C. For min/max values, TJ = −40°C to +125°C, VCC = 15 V,
IFB = 100 mA, Ivac = 30 mA, IS = 0 mA, unless otherwise specified)
Characteristics UnitMaxTypMinSymbolPin
SUPPLY SECTION
Supply Voltage
UVLO Startup Threshold
Minimum Operating Voltage after Startup
UVLO Hysteresis
8
VCC(on)
VCC(off)
VCC(H)
12.25
8.0
4.0
13.25
8.7
4.55
14.5
9.5
−
V
V
V
Supply Current:
Startup (VCC = VCC(on) − 0.2 V)
Startup (VCC < 8.0 V, IFB = 200 mA)
Startup (8.0 V < VCC < VCC(on) − 0.2 V, IFB = 200 mA)
Startup (VCC < VCC(on) − 0.2 V, IFB = 0 mA) (Note 5)
Operating (VCC = 15 V, Drv = open, VM = 3 V)
Operating (VCC = 15 V, Drv = 1 nF to Gnd, VM = 1 V)
Shutdown (VCC = 15 V and IFB = 0 A)
8
Istup
Istup1
Istup2
Istup3
ICC1
ICC2
Istdn
−
−
−
−
−
−
−
18
0.95
21
21
3.7
4.7
33
50
1.5
50
50
5.0
6.0
50
mA
mA
mA
mA
mA
mA
mA
Product parametric performance is indicated in the Electrical Characteristics for the listed test conditions, unless otherwise noted. Product
performance may not be indicated by the Electrical Characteristics if operated under different conditions.
5. Please refer to the “Biasing the Controller” Section in the Functional Description.
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TYPICAL CHARACTERISTICS
fSW, SWITCHING FREQUENCY (kHz)
Figure 3. Switching Frequency vs. Temperature
TJ, JUNCTION TEMPERATURE (°C)
60
65
70
75
80
85
90
−50 0 25 50 75 100 125
Figure 4. Maximum Duty Cycle vs. Temperature
Figure 5. Gate Drive Resistance vs. Temperature Figure 6. Reference Current vs. Temperature
−25
95
100
105
110
Dmax, MAXIMUM DUTY CYCLE (%)
TJ, JUNCTION TEMPERATURE (°C)
90
91
92
93
94
95
96
−50 0 25 50 75 100 125
−25
97
VM = 0 V
ROH & ROL, GATE DRIVE RESISTANCE (W)
TJ, JUNCTION TEMPERATURE (°C)
0
2
4
6
−50 0 25 50 75 100 125
−25
8
10
Iref, REFERENCE CURRENT (mA)
TJ, JUNCTION TEMPERATURE (°C)
195
196
197
198
199
200
201
−50 0 25 50 75 100 125
−25
202
ROH
203
205
98
99
100
12
14
ROL
204
NCP1653
NCP1653A
IFB:‘00)4A \ T J : —40‘C U 25 2%?
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TYPICAL CHARACTERISTICS
MAXIMUM CONTROL VOLTAGE (V)
TJ, JUNCTION TEMPERATURE (°C)
2.0
2.2
2.4
2.6
2.8
3.0
−50 0 25 50 75 100 125
−25
FEEDBACK PIN VOLTAGE (V)
IFB, FEEDBACK PIN CURRENT (mA)
1
1.5
2
2.5
50 100 150 200 250
0
OVERVOLTAGE PROTECTION RATIO (%)
TJ, JUNCTION TEMPERATURE (°C)
100
102
104
106
108
110
112
−50 0 25 50 75 100 125
−25
114
116
120
TJ = 25°C
0
0.5
118
TJ = −40°C
TJ = 125°C
Vcontrol, CONTROL VOLTAGE (V)
Figure 7. Regulation Block Figure 8. Regulation Block Ratio vs.
Temperature
0
0.5
1
1.5
2
3
100 120 140 160 180 200 220
IFB, FEEDBACK CURRENT (mA)
TJ = 25°C
2.5
TJ = 125°C
TJ = −40°C
Figure 9. Maximum Control Voltage vs.
Temperature
Figure 10. Feedback Pin Voltage vs.
Temperature
Figure 11. Feedback Pin Voltage vs. Feedback
Current
Figure 12. Overvoltage Protection Ratio
vs. Temperature
REGULATION BLOCK RATIO (%)
TJ, JUNCTION TEMPERATURE (°C)
90
91
92
93
94
95
96
−50 0 25 50 75 100 125
−25
97
98
99
100
FEEDBACK PIN VOLTAGE (V)
TJ, JUNCTION TEMPERATURE (°C)
1
1.5
2
2.5
−25 0 25 100 125
−50
0
0.5
IFB = 200 mA
2.1
2.3
2.5
2.7
2.9
50 75
IFB = 100 mA
ac : 100 “A | :muA
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TYPICAL CHARACTERISTICS
CURRENT SENSE PIN VOLTAGE (mV)
IS, SENSE CURRENT (mA)
0
20
40
60
80
100
0100 150 200 250
50
TJ = −40 °C
OVERPOWER LIMITATION THRESHOLD (nA2)
TJ, JUNCTION TEMPERATURE (°C)
−50 0 25 50 75 100 125
−25
Vvac, IN PIN VOLTAGE (V)
Ivac, INPUT−VOLTAGE CURRENT (mA)
0
1
2
3
4
5
6
0 50 150100 200
7
0
0.5
1
1.5
2
2.5
3
3.5
4
TJ = 25 °C
TJ = 125 °C
Figure 13. Overvoltage Protection Threshold
vs. Temperature
Figure 14. Undervoltage Protection
Thresholds vs. Temperature
OVERVOLTAGE PROTECTION THRESHOLD (mA)
TJ, JUNCTION TEMPERATURE (°C)
220
225
230
−50 0 25 50 75 100 125
−25
UNDERVOLTAGE PROTECTION
THRESHOLD RATIO (%)
TJ, JUNCTION TEMPERATURE (°C)
0
2
4
6
8
10
12
−50 0 25 50 75 100 125
−25
14
16
200
205
210
215
Figure 15. Current Sense Pin Voltage vs.
Sense Current
Figure 16. Overcurrent Protection Threshold
vs. Temperature
Figure 17. Overpower Limitation Threshold
vs. Temperature
Figure 18. In Pin Voltage vs.
Input−Voltage Current
OVERCURRENT PROTECTION
THRESHOLD (mA)
TJ, JUNCTION TEMPERATURE (°C)
198
200
202
204
206
208
210
−50 0 25 50 75 100 12
5
−25
190
192
194
196
Ivac = 100 mA
Ivac = 30 mATJ = −40 °C
TJ = 25 °C
TJ = 125 °C
IUVP(off)/Iref
IUVP(on)/Iref
10
30
50
70
90
um. No Load
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TYPICAL CHARACTERISTICS
10% OF MAXIMUM CONTROL CURRENT (mA)
TJ, JUNCTION TEMPERATURE (°C)
0
4
8
12
−50 0 25 50 75 100 125
−25
SUPPLY VOLTAGE UNDERVOLTAGE
LOCKOUT THRESHOLDS (V)
TJ, JUNCTION TEMPERATURE (°C)
0
2
4
6
8
10
12
−50 0 25 50 75 100 125
−25
VCC = 15 V
Istdn
VCC(on)
VCC(off)
Istup
SUPPLY CURRENT IN STARTUP AND
SHUTDOWN MODE (mA)
TJ, JUNCTION TEMPERATURE (°C)
0
10
20
30
40
50
70
−50 0 25 50 75 100 125
−25
OPERATING SUPPLY CURRENT (mA)
TJ, JUNCTION TEMPERATURE (°C)
0
1
2
3
4
5
−50 0 25 50 75 100 12
5
−25
2
6
10
60 ICC2, 1 nF Load
ICC1, No Load
Figure 19. PWM Comparator Reference
Voltage vs. Temperature
Figure 20. Maximum Control Current vs.
Temperature
PWM COMPARATOR REF. VOLTAGE (V)
TJ, JUNCTION TEMPERATURE (°C)
2
2.1
2.2
2.3
2.4
2.5
2.7
−50 0 25 50 75 100 125
−25
MAXIMUM CONTROL CURRENT (mA)
TJ, JUNCTION TEMPERATURE (°C)
0
20
40
60
80
100
140
−50 0 25 50 75 100 125
−25
2.6 120
160
180
Figure 21. 10% of Maximum Control Current
vs. Temperature
Figure 22. Supply Voltage Undervoltage
Lockout Thresholds vs. Temperature
Figure 23. Supply Current in Startup and
Shutdown Mode vs. Temperature
Figure 24. Operating Supply Current vs.
Temperature
2.8
3
2.9
Ivac = 30 mA
Vcontrol = Vcontrol(max)
IS = 25 mA
IS = 75 mA
Ivac = 30 mA
Vcontrol = 10 % Vcontrol(max)
IS = 25 mA
IS = 75 mA
14
16
80 6
Icontrol = derived from the (eq.8)
IS Ivac
2IM
Icontrol = derived from the (eq.8)
IS Ivac
2IM
200
16
20
14
18 18
20
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FUNCTIONAL DESCRIPTION
Introduction
The NCP1653 is a Power Factor Correction (PFC) boost
controller designed to operate in fixed−frequency
Continuous Conduction Mode (CCM). It can operate in
either peak current−mode or average current−mode.
Fixed−frequency operation eases the compliance with
EMI standards and the limitation of the possible radiated
noise that may pollute surrounding systems. The CCM
operation reduces the application di/dt and the resulting
interference. The NCP1653 is designed in a compact 8−pin
package which offers the minimum number of external
components. It simplifies the design and reduces the cost.
The output stage of the NCP1653 incorporates ±1.5 A
current capability for direct driving of the MOSFET in
high−power applications.
The NCP1653 is implemented in constant output voltage
or follower boost modes. The follower boost mode permits
one to significantly reduce the size of the PFC circuit
inductor and power MOSFET. With this technique, the
output voltage is not set at a constant level but depends on
the RMS input voltage or load demand. It allows lower
output voltage and hence the inductor and power MOSFET
size or cost are reduced.
Hence, NCP1653 is an ideal candidate in high−power
applications where cost−effectiveness, reliability and high
power factor are the key parameters. The NCP1653
incorporates all the necessary features to build a compact
and rugged PFC stage.
The NCP1653 provides the following protection features:
1. Overvoltage Protection (OVP) is activated and
the Drive Output (Pin 7) goes low when the
output voltage exceeds 107% of the nominal
regulation level which is a user−defined value.
The circuit automatically resumes operation when
the output voltage becomes lower than the 107%.
2. Undervoltage Protection (UVP) is activated and
the device is shut down when the output voltage
goes below 8% of the nominal regulation level.
The circuit automatically starts operation when
the output voltage goes above 12% of the
nominal regulation level. This feature also
provides output open−loop protection, and an
external shutdown feature.
3. Overpower Limitation (OPL) is activated and the
Drive Output (Pin 7) duty ratio is reduced by
pulling down an internal signal when a computed
input power exceeds a permissible level. OPL is
automatically deactivated when this computed input
power becomes lower than the permissible level.
4. Overcurrent Protection (OCP) is activated and
the Drive Output (Pin 7) goes low when the
inductor current exceeds a user−defined value.
The operation resumes when the inductor current
becomes lower than this value.
5. Thermal Shutdown (TSD) is activated and the
Drive Output (Pin 7) is disabled when the
junction temperature exceeds 150_C. The
operation resumes when the junction temperature
falls down by typical 30_C.
CCM PFC Boost
A CCM PFC boost converter is shown in Figure 25. The
input voltage is a rectified 50 or 60 Hz sinusoidal signal.
The MOSFET is switching at a high frequency (typically
102 kHz in the NCP1653) so that the inductor current IL
basically consists of high and low−frequency components.
Filter capacitor Cfilter is an essential and very small value
capacitor in order to eliminate the high−frequency
component of the inductor current IL. This filter capacitor
cannot be too bulky because it can pollute the power factor
by distorting the rectified sinusoidal input voltage.
Figure 25. CCM PFC Boost Converter
Vin
Iin ILL
Vout
Cbulk
Cfilter
PFC Methodology
The NCP1653 uses a proprietary PFC methodology
particularly designed for CCM operation. The PFC
methodology is described in this section.
Figure 26. Inductor Current in CCM
Iin
t2
t1time
T
IL
As shown in Figure 26, the inductor current IL in a
switching period T includes a charging phase for duration
t1 and a discharging phase for duration t2. The voltage
conversion ratio is obtained in (eq.1).
Vout
Vin +t1)t2
t2+T
T*t1
Vin +T*t1
TVout (eq.1)
Vin 7 ii Voul |1 , I1 VM Voui V I .I|—) H Figure 27. PFC Duty Modulation and Timing Diagram The PFC duiy mnriuiarirrii and iimirig diagram is shown in Figure 27. The MOSFET on iime i, is gciicraicd by Ihc inicneciion of reference volmgc er and ramp vnllage vmmpr A rclmiorisliip iii (cq.4) is obtained 'chfi Cramp Vramp = VM + = Vref ieaA) The charging currcm id is specially designed as in (eq.5). The mulliplicr vulmgc vM is ihcrcforc expressed in Icrms of i. in (Cqfi). Cram Vref leh = + ieafii r. I Figure 29. 2 |
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The input filter capacitor Cfilter and the front−ended EMI
filter absorbs the high−frequency component of inductor
current IL. It makes the input current Iin a low−frequency
signal only of the inductor current.
Iin +IL−50 (eq.2)
The suffix 50 means it is with a 50 or 60 Hz bandwidth
of the original IL.
From (eq.1) and (eq.2), the input impedance Zin is
formulated.
Zin +Vin
Iin +T*t1
T
Vout
IL−50
(eq.3)
Power factor is corrected when the input impedance Zin
in (eq.3) is constant or slowly varying in the 50 or 60 Hz
bandwidth.
Figure 27. PFC Duty Modulation and Timing Diagram
R
S
Q
0 1
clock
PFC Modulation
Output
Clock
Latch Set
Latch Reset
Inductor
Current
without
filtering
−
+
+
Vref
Vref
Vramp
Vramp
VM
VM
VM
Ich
Cramp
The PFC duty modulation and timing diagram is shown
in Figure 27. The MOSFET on time t1 is generated by the
intersection of reference voltage Vref and ramp voltage
Vramp. A relationship in (eq.4) is obtained.
Vramp +VM)Icht1
Cramp +Vref (eq.4)
The charging current Ich is specially designed as in
(eq.5). The multiplier voltage VM is therefore expressed in
terms of t1 in (eq.6).
Ich +Cramp Vref
T
(eq.5)
(eq.6)
VM+Vref *t1
Cramp
CrampVref
T+Vref T*t1
T
From (eq.3) and (eq.6), the input impedance Zin is
re−formulated in (eq.7).
(eq.7)
Zin +VM
Vref
Vout
IL−50
Because Vref and Vout are roughly constant versus time,
the multiplier voltage VM is designed to be proportional to
the IL−50 in order to have a constant Zin for PFC purpose.
It is illustrated in Figure 28.
Figure 28. Multiplier Voltage Timing Diagram
Vin
time
time
VM
time
Iin
IL
It can be seen in the timing diagram in Figure 27 that VM
originally consists of a switching frequency ripple coming
from the inductor current IL. The duty ratio can be
inaccurately generated due to this ripple. This modulation
is the so−called “peak current−mode”. Hence, an external
capacitor CM connected to the multiplier voltage VM pin
(Pin 5) is essential to bypass the high−frequency
component of VM. The modulation becomes the so−called
“average current−mode” with a better accuracy for PFC.
Figure 29. External Connection on the Multiplier
Voltage Pin
5RM Ivac IS
2Icontrol
VM =
PFC Duty
Modulation
IM
VM
RM
CM
The multiplier voltage VM is generated according to
(eq.8).
VM+RMIvac IS
2I
control (eq.8)
Input−voltage current Ivac is proportional to the RMS
input voltage Vac as described in (eq.9). The suffix ac
‘E Vac ! (2‘ R' R05 R Vcomrol 2 n 500 kg f 2 R R’ I V I 2R R' | V
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stands for the RMS. Ivac is a constant in the 50 or 60 Hz
bandwidth. Multiplier resistor RM is the external resistor
connected to the multiplier voltage VM pin (Pin 5). It is also
constant. RM directly limits the maximum input power
capability and hence its value affects the NCP1653 to
operate in either “follower boost mode” or “ constant
output voltage mode”.
Ivac +2
ǸVac *4V
ǒRvac )12 kWǓ[Vac
RȀvac
(eq.9)
Sense current IS is proportional to the inductor current IL
as described in (eq.10). IL consists of the high−frequency
component (which depends on di/dt or inductor L) and
low−frequency component (which is IL−50).
IS+RCS
RSIL(eq.10)
Control current Icontrol is a roughly constant current that
comes from the PFC output voltage Vout that is a slowly
varying signal. The bandwidth of Icontrol can be
additionally limited by inserting an external capacitor
Ccontrol to the control voltage Vcontrol pin (Pin 2) in
Figure 30. It is recommended to limit fcontrol, that is the
bandwidth of Vcontrol (or Icontrol), below 20 Hz typically to
achieve power factor correction purpose. Typical value of
Ccontrol is between 0.1 mF and 0.33 mF.
Figure 30. Vcontrol Low−Pass Filtering
FB
ref ref
reg
300 k
Ccontrol
V
II
96% I
Regulation Block
2
Vcontrol
I =
control
Vcontrol
R1
(eq.11)
Ccontrol u1
2p300 kWfcontrol
From (eq.7)−(eq.10), the input impedance Zin is
re−formulated in (eq.12).
Zin +RMRCS Vac Vout IL
2R
SRȀvac Icontrol Vref IL−50
Zin +RMRCS Vac Vout
2R
SRȀvac Icontrol Vref whenIL+IL−50 (eq.12)
The multiplier capacitor CM is the one to filter the
high−frequency component of the multiplier voltage VM.
The high−frequency component is basically coming from
the inductor current IL. On the other hand, the filter
capacitor Cfilter similarly removes the high−frequency
component of inductor current IL. If the capacitors CM and
Cfilter match with each other in terms of filtering capability,
IL becomes IL−50. Input impedance Zin is roughly constant
over the bandwidth of 50 or 60 Hz and power factor is
corrected.
Practically, the differential−mode inductance in the
front−ended EMI filter improves the filtering performance
of capacitor Cfilter. Therefore, the multiplier capacitor CM
is generally with a larger value comparing to the filter
capacitor Cfilter.
Input and output power (Pin and Pout) are derived in
(eq.13) when the circuit efficiency η is obtained or
assumed. The variable Vac stands for the RMS input
voltage.
Pin +Vac2
Zin +2R
SRȀvac Icontrol Vref Vac
RMRCS Vout
(eq.13a)
TIcontrol Vac
Vout
Pout +hPin +h2R
SRȀvac Icontrol Vref Vac
RMRCS Vout
(eq.13b)
TIcontrol Vac
Vout
Follower Boost
The NCP1653 operates in follower boost mode when
Icontrol is constant. If Icontrol is constant based on (eq.13), for
a constant load or power demand the output voltage Vout of
the converter is proportional to the RMS input voltage Vac. It
means the output voltage Vout becomes lower when the RMS
input voltage Vac becomes lower. On the other hand, the
output voltage Vout becomes lower when the load or power
demand becomes higher. It is illustrated in Figure 31.
Figure 31. Follower Boost Characteristics
Vin
V (Follower boost)
out
time
time
V (Traditional boost)
out
Pout
Follower Boost Benefits
The follower boost circuit offers an opportunity to reduce
the output voltage Vout whenever the RMS input voltage
Vac is lower or the power demand Pout is higher. Because
of the step−up characteristics of boost converter, the output
voltage Vout will always be higher than the input voltage
Vin even though Vout is reduced in follower boost operation.
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As a result, the on time t1 is reduced. Reduction of on time
makes the loss of the inductor and power MOSFET smaller.
Hence, it allows cheaper cost in the inductor and power
MOSFET or allows the circuit components to operate at a
lower stress condition in most of the time.
Output Feedback
The output voltage Vout of the PFC circuit is sensed as a
feedback current IFB flowing into the FB pin (Pin 1) of the
device. Since the FB pin voltage VFB1 is much smaller than
Vout, it is usually neglected.
(eq.14)
IFB +Vout *VFB1
RFB [Vout
RFB
where RFB is the feedback resistor across the FB pin
(Pin 1) and the output voltage referring to Figure 2.
Then, the feedback current IFB represents the output
voltage Vout and will be used in the output voltage
regulation, undervoltage protection (UVP), and
overvoltage protection (OVP).
Output Voltage Regulation
Feedback current IFB which represents the output voltage
Vout is processed in a function with a reference current
(Iref = 200 mA typical) as shown in regulation block
function in Figure 32. The output of the voltage regulation
block, low−pass filter on Vcontrol pin and the Icontrol =
Vcontrol / R1 block is in Figure 30 is control current Icontrol.
And the input is feedback current IFB. It means that Icontrol
is the output of IFB and it can be described as in Figure 32.
There are three linear regions including: (1) IFB < 96% ×
Iref, (2) 96% × Iref <IFB < Iref, and (3) IFB > Iref. They are
discussed separately as follows:
Figure 32. Regulation Block
Icontrol
Iref
Iref
96% IFB
Icontrol(max)
Region (1): IFB < 96% × Iref
When IFB is less than 96% of Iref (i.e., Vout < 96% RFB
× Iref), the NCP1653 operates in follower boost mode. The
regulation block output Vreg is at its maximum value.
Icontrol becomes its maximum value (i.e., Icontrol =
Icontrol(max) = Iref/2 = 100 mA) which is a constant. (eq.13)
becomes (eq.15).
Vout +h2R
SRȀvac Icontrol(max) Vref Vac
RMRCS Pout
(eq.15)
TVac
Pout
The output voltage Vout is regulated at a particular level
with a particular value of RMS input voltage Vac and output
power Pout. However, this output level is not constant and
depending on different values of Vac and Pout. The follower
boost operating area is illustrated in Figure 33.
Figure 33. Follower Boost Region
V
VV
Vout
ac(max)
ac(min) ac
Pout(min) Pout(max)
12
Vin
96% Iref RFB
1. Pout increases, Vout decreases
2. Vac decreases, Vout decreases
Region (2): 96% × Iref < IFB < Iref
When IFB is between 96% and 100% of Iref (i.e., 96% RFB
× Iref < Vout < RFB × Iref), the NCP1653 operates in constant
output voltage mode which is similar to the follower boost
mode characteristic but with narrow output voltage range.
The regulation block output Vreg decreases linearly with
IFB in the range from 96% of Iref to Iref. It gives a linear
function of Icontrol in (eq.16).
(eq.16)
Icontrol +Icontrol(max)
0.04 ǒ1*Vout
RFB IrefǓ
Resolving (eq.16) and (eq.13),
Vout +Vac
ǒRMRCS
2R
SRȀvac Vref
0.04
Icontrol(max)
Pout
h)Vac
RFB IrefǓ(eq.17)
According to (eq.17), output voltage Vout becomes RFB
× Iref when power is low (Pout ≈ 0). It is the maximum value
of Vout in this operating region. Hence, it can be concluded
that output voltage increases when power decreases. It is
similar to the follower boost characteristic in (eq.15). On
the other hand in (eq.17), output voltage Vout becomes RFB
× Iref when RMS input voltage Vac is very high. It is the
maximum value of Vout in this operating region. Hence, it
can also be concluded that output voltage increases when
RMS input voltage increases. It is similar to another
follower boost characteristic in (eq.15). This characteristic
is illustrated in Figure 34.
Figure 34. Constant Output Voltage Region
V
VV
Vout
ac(max)
ac(min) ac
P
out(min) Pout(max)
12
96% Iref RFB
1. Pout increases, Vout decreases
2. Vac decreases, Vout decreases
Iref RFB
Region (3): IFB > Iref
When IFB is greater than Iref (i.e., Vout > RFB × Iref), the
NCP1653 provides no output or zero duty ratio. The
regulation block output Vreg becomes 0 V. Icontrol also
becomes zero. The multiplier voltage VM in (eq.8)
\I II
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14
becomes its maximum value and generates zero on time t1.
Then, Vout decreases and the minimum can be Vout = Vin in
a boost converter. Going down to Vin, Vout automatically
enters the previous two regions (i.e., follower boost region
or constant output voltage region) and hence output voltage
Vout cannot reach input voltage Vin as long as the NCP1653
provides a duty ratio for the operation of the boost
converter.
In conclusion, the NCP1653 circuit operates in one of the
following conditions:
Constant output voltage mode: The output voltage is
regulated around the range between 96% and 100% of RFB
× I
ref. The output voltage is described in (eq.16). Its
behavior is similar to a follower boost.
Follower boost mode: The output voltage is regulated
under 96% of RFB × Iref and Icontrol = Icontrol(max) = Iref/2 =
100 mA. The output voltage is described in (eq.15).
Overvoltage Protection (OVP)
When the feedback current IFB is higher than 107% of the
reference current Iref (i.e., Vout > 107% RFB × Iref ), the
Drive Output (Pin 7) of the device goes low for protection.
The circuit automatically resumes operation when the
feedback current becomes lower than 107% of the
reference current Iref.
The maximum OVP threshold is limited to 230 mA which
corresponds to 230 mA × 1.92 MW + 2.5 V = 444.1 V when
RFB = 1.92 MW (680 kW + 680 kW + 560 kW) and
VFB1 = 2.5 V (for the worst case referring to Figure 11).
Hence, it is generally recommended to use 450 V rating
output capacitor to allow some design margin.
Undervoltage Protection (UVP)
Figure 35. Undervoltage Protection
I
8% I 12% I FB
Shutdown Operating
ref
ref
ICC
ICC2
Istdn
When the feedback current IFB is less than 8% of the
reference current Iref (i.e., the output voltage Vout is less
than 8% of its nominal value), the device is shut down and
consumes less than 50 mA. The device automatically starts
operation when the output voltage goes above 12% of the
nominal regulation level. In normal situation of boost
converter configuration, the output voltage Vout is always
greater than the input voltage Vin and the feedback current
IFB is always greater than 8% and 12% of the nominal level
to enable the NCP1653 to operate. Hence, UVP happens
when the output voltage is abnormally undervoltage, the
FB pin (Pin 1) is opened, or the FB pin (Pin 1) is manually
pulled low.
Soft−Start
The device provides no output (or no duty ratio) when the
Vcontrol (Pin 2) voltage is zero (i.e., Vcontrol = 0 V). An
external capacitor Ccontrol connected to the Vcontrol pin
provides a gradually increment of the Vcontrol voltage (or
the duty ratio) in the startup and hence provides a soft−start
feature.
Current Sense
The device senses the inductor current IL by the current
sense scheme in Figure 36. The device maintains the
voltage at the CS pin (Pin 4) to be zero voltage (i.e.,
VS ≈ 0 V) so that (eq.10) can be formulated.
Figure 36. Current Sensing
CS NCP1653
Gnd
+
−
RCS
RS
IL
IS
IL
VS
This scheme has the advantage of the minimum number
of components for current sensing and the inrush current
limitation by the resistor RCS. Hence, the sense current IS
represents the inductor current IL and will be used in the
PFC duty modulation to generate the multiplier voltage
VM, Overpower Limitation (OPL), and overcurrent
protection.
Overcurrent Protection (OCP)
Overcurrent protection is reached when IS is larger than
IS(OCP) (200 mA typical). The offset voltage of the CS pin
is typical 10 mV and it is neglected in the calculation.
Hence, the maximum OCP inductor current threshold
IL(OCP) is obtained in (eq.15).
(eq.18)
IL(OCP) +RSIS(OCP)
RCS +RS
RCS 200 mA
When overcurrent protection threshold is reached, the
Drive Output (Pin 7) of the device goes low. The device
automatically resumes operation when the inductor current
goes below the threshold.
Input Voltage Sense
The device senses the RMS input voltage Vac by the
sensing scheme in Figure 37. The internal current mirror is
with a typical 4 V offset voltage at its input so that the
current Ivac can be derived in (eq.9). An external capacitor
Cvac is to maintain the In pin (Pin 3) voltage in the
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calculation to always be the peak of the sinusoidal voltage
due to very little current consumption (i.e., Vin = √2 Vac and
Ivac ≈ 0). This Ivac current represents the RMS input voltage
Vac and will be used in overpower limitation (OPL) and the
PFC duty modulation.
Figure 37. Input Voltage Sensing
In
Current
Mirror
3
12 k
Cvac
Rvac
Ivac 4 V
Vin
9 V
There is an internal 9 V ESD Zener Diode on the pin.
Hence, the value of Rvac is recommended to be at least
938 kW for possibly up to 400 V instantaneous input voltage.
Rvac
400 V *9Vu12 kW
9V*4V
(eq.19)
Rvac u938 kW
Overpower Limitation (OPL)
Sense current IS represents the inductor current IL and
hence represents the input current approximately.
Input−voltage current Ivac represents the RMS input
voltage Vac and hence represents the input voltage. Their
product (IS × Ivac) represents an approximated input power
(IL × Vac).
Figure 38. Overpower Limitation Reduces Vcontrol
FB
ref ref
reg
300 k
Vcontrol
V
II
96% I
Limitation
Overpower
Regulation Block
2
0 1
When the product (IS × Ivac) is greater than a permissible
level 3 nA2, the output Vreg of the regulation block is pulled
to 0 V. It makes Vcontrol to be 0 V indirectly and VM is
pulled to be its maximum. It generates the minimum duty
ratio or no duty ratio eventually so that the input power is
limited. The OPL is automatically deactivated when the
product (IS × Ivac) becomes lower than the 3 nA2 level. This
3 nA2 level corresponds to the approximated input power
(IL × V
ac) to be smaller than the particular expression in
(eq.20).
ISIvac t3nA
2
ǒIL@RCS
RSǓ ǒVac @2
Ǹ
Rvac )12 kWǓt3nA
2
IL@Vac tRS
RCS
Rvac )12 kW
2
Ǹ3nA
2(eq.20)
Biasing the Controller
It is recommended to add a typical 1 nF to 100 nF
decoupling capacitor next to the VCC pin for proper operation.
When the NCP1653 operates in follower boost mode, the PFC
output voltage is not always regulated at a particular level
under all application range of input voltage and load power.
It is not recommended to make a low−voltage bias supply
voltage by adding an auxiliary winding on the PFC boost
inductor. Alternatively, it is recommended to get the VCC
biasing supply from the second−stage power conversion stage
as shown in Figure 39.
Figure 39. Recommended Biasing Scheme in
Follower Boost Mode
AC
Input
Output
EMI
Filter
NCP1653
V
cc
V
bulk
Second−stage
Power Converter
Voltage
When the NCP1653 operates in constant output voltage
mode, it is possible to make a low−voltage bias supply by
adding an auxiliary winding on the PFC boost inductor in
Figure 40. In PFC boost circuit, the input is the rectified AC
voltage and it is non−constant versus time that makes the
auxiliary winding voltage also non−constant. Hence, the
configuration in Figure 40 charges the voltages in
capacitors C1 and C2 to n×(Vout − Vin) and n×Vin and n is
the turn ratio. As a result, the stack of the voltages is n×Vout
that is constant and can be used as a biasing voltage.
r7 www.cmsem om _}__|_ _|_ kl .—o .=L_L_L |\ |\ r7 r7
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Figure 40. Self−biasing Scheme in Constant Output
Voltage Mode
V
C1C2
out
Vin
VCC
When the NCP1653 circuit is required to be startup
independently from the second−stage converter, it is
recommended to use a circuit in Figure 41. When there is
no feedback current (IFB = 0 mA) applied to FB pin (Pin 1),
the NCP1653 VCC startup current is as low (50 mA
maximum). It is good for saving the current to charge the
VCC capacitor. However, when there is some feedback
current the startup current rises to as high as 1.5 mA in the
VCC < 4 V region. That is why the circuit of Figure 41 can
be implemented: a PNP bipolar transistor derives the
feedback current to ground at low VCC levels (VCC < 4 V)
so that the startup current keeps low and an initial voltage
can be quickly built up in the VCC capacitor. The values in
Figure 41 are just for reference.
Figure 41. Recommended Startup Biasing Scheme
180k
NCP1653
100uF
560k
Input Output
1.5M
180k
180k
BC556
VCC Undervoltage Lockout (UVLO)
The device typically starts to operate when the supply
voltage VCC exceeds 13.25 V. It turns off when the supply
voltage VCC goes below 8.7 V. An 18 V internal ESD Zener
Diode is connected to the VCC pin (Pin 8) to prevent
excessive supply voltage. After startup, the operating range
is between 8.7 V and 18 V.
Thermal Shutdown
An internal thermal circuitry disables the circuit gate
drive and then keeps the power switch off when the junction
temperature exceeds 150_C. The output stage is then
enabled once the temperature drops below typically 120_C
(i.e., 30_C hysteresis). The thermal shutdown is provided
to prevent possible device failures that could result from an
accidental overheating.
Output Drive
The output stage of the device is designed for direct drive
of power MOSFET. It is capable of up to ±1.5 A peak drive
current and has a typical rise and fall time of 88 and
61.5 ns with a 2.2 nF load.
. o—m NY‘ rm W H O ,i see nF :: H— ,_. 4.7 M . C d O SFPEONSOS \I n 470 k m ‘5 v NCP1653 235 k .4: 0 II— 4.5 .— —. ._ A r j ._ A .— —. ._ 4 aaonT InF;:;:1nF aaon;: 56k ‘Ok Figure 42. 300 W 100 kHz Power Factor Correction Circuit
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17
Application Schematic
Figure 42. 300 W 100 kHz Power Factor Correction Circuit
450 V
1 nF 1 nF 330 pF
4.7 M
0.1
NCP1653
390 V
470 k
Fuse
SPP20N60S
Output
56 k
2.85 k
10 k
4.5
330 nF
15 V
KBU6K
680 nF
Input
90 Vac
to
265 Vac
1 mF100 mF
CSD04060
150 mH
2 x 3.9 mH
100 nF
680 k 680 k 560 k
600 mH
33 nF
Table 1. Total Harmonic Distortion and Efficiency
Input Voltage
(V)
Input Power
(W)
Output Voltage
(V)
Output Current
(A)
Power Factor Total Harmonic
Distortion (%)
Efficiency
(%)
110 331.3 370.0 0.83 0.998 4 93
110 296.7 373.4 0.74 0.998 4 93
110 157.3 381.8 0.38 0.995 7 92
110 109.8 383.5 0.26 0.993 9 91
110 80.7 384.4 0.19 0.990 10 91
110 67.4 385.0 0.16 0.988 10 91
220 311.4 385.4 0.77 0.989 9 95
220 215.7 386.2 0.53 0.985 8 95
220 157.3 386.4 0.38 0.978 9 93
220 110.0 386.7 0.27 0.960 11 95
220 80.2 386.5 0.19 0.933 14 92
220 66.9 386.6 0.16 0.920 15 92
Voul h + I2 V I Voui Vin H ll V I +| Lei VOL“ Voui Vin Vin 7 F‘MFiCSVaicVoul Vac RSR'vachef 'conileac Vac Vac ”A E i 2 ‘2
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APPENDIX I – SUMMARY OF EQUATIONS IN NCP1653 BOOST PFC
Description Follower Boost Mode Constant Output Voltage Mode
Boost Converter Vout
Vin +t1)t2
t2+T
T*t1
Same as Follower Boost Mode
³Vout *Vin
Vout +t1
t1)t2+t1
T
Input Current Averaged by
Filter Capacitor Iin +IL*50 Same as Follower Boost Mode
Nominal Output Voltage (IFB
= 200 mA) Vout(nom) +IFBRFB )VFB1
[IFBRFB +200 mA@RFB
Same as Follower Boost Mode
Feedback Pin Voltage VFB1 Please refer to Figure 11. Same as Follower Boost Mode
Output Voltage Vin tVout t192 mA@RFB 192 mA@RFB tVout t200 mA@RFB
Inductor Current
Peak−Peak Ripple DIL(pk *pk) t2@IL*50 Same as Follower Boost Mode
Control Current Icontrol +Icontrol(max) +Iref
2+100 mAIcontrol +Icontrol(max)
0.04 ǒ1*Vout
RFBIrefǓ
and Icontrol tIcontrol(max) +100 mA
Switching Frequency f+67 or 100 kHz Same as Follower Boost Mode
Minimum Inductor for CCM LuL(CRM) +Vout *Vin
Vout
Vin
DIL(pk *pk)
1
f
Same as Follower Boost Mode
Input Impedance Zin +RMRCSVacVout
RSRȀvacIrefVref Zin +RMRCS Vac Vout
2RSRȀvac Icontrol Vref
Input Power
Pin +RSRȀvac Iref Vref
RMRCS
Vac
Vout
Pin +2RSRȀvacVref
RMRCS
IcontrolVac
Vout
Output Power
Pout +hPin +hRSRȀvac Iref Vref
RMRCS
Vac
Vout Pout +h2R
SRȀvac Vref
RMRCS
Icontrol Vac
Vout
Maximum Input Power when
Icontrol = 100 mAPin(max) +Pin +RSRȀvac Iref Vref
RMRCS
Vac
Vout
Circuit will enter follower boost region when
maximum power is reached.
Current Limit IL(OCP) +RS
RCS @200 mASame as Follower Boost Mode
Power Limit
IL@VAC tRS
RCS
Rvac )12 kW
2
Ǹ@3nA
2Same as Follower Boost Mode
Output Overvoltage Vout(OVP) +107% @Vout(nom)
[214 mA@RFB
Same as Follower Boost Mode
Output Undervoltage Vout(UVP *on) +8% @Vout(nom)
[16 mA@RFB
Vout(UVP *off) +12% @Vout(nom)
[24 mA@RFB
Same as Follower Boost Mode
Input Voltage Sense Pin
Resistor Rvac Rvac u938 kWand RȀvac +Rvac )12 kW
2
Ǹ
Same as Follower Boost Mode
PWM Comparator
Reference Voltage Vref +2.62 V Same as Follower Boost Mode
NCP1653, NCP1653A
www.onsemi.com
19
ORDERING INFORMATION
Device Package Shipping†Switching Frequency
NCP1653PG PDIP−8
(Pb−Free)
50 Units / Rail 100 kHz
NCP1653DR2G SO−8
(Pb−Free)
2500 Units / Tape & Reel
NCP1653APG PDIP−8
(Pb−Free)
50 Units / Rail 67 kHz
NCP1653ADR2G SO−8
(Pb−Free)
2500 Units / Tape & Reel
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
um: E RD I'HH'HIHHH'I I I 5 77+77 , E1 4° I I LHHHIHHHJ mm .3 TOP VIEW «Bxb SIDE VIEW 1 SEATING PLANE aw END VIEW wmI LEADS cousIIAAIIIED a TES DIMEHsIoNINC A CONTROLLING D DIMENSIONS A ACE sEAIED IN DIMENSIONS D 0R PnomusI TO EXCEED a DIMENSION E PLANE H WIT TO DATUM c DIMENSION E3 Is MEAsuH LEADS uHcoNsmAINED DATUM PLANE H Is CCIHCIDENT WITH IHE a LEADS. WHERE THE LEADS EXIT THE Dom PACKAGE CONTOUR IS OPUONAL IRouNDED OR souAHE CORNERS) IIIcIIEs MILLIMEYERS DIM MIN MAX Mm MAX A D 2I a 5 3: AI D m 5 a 33 mm DD22 ass ass a asD TVP I 52 TVP 0355 mm 922 ID Is I DUDE a I: E 03m) 0325 752 825 EI 0240 Dzan 5m 7n I2 I22 c Imus um um ass D D “T ‘ e a ma ass 2 54 I350 25 ‘ ea me “192 END VIEW M In In www onsem com 20
NCP1653, NCP1653A
www.onsemi.com
20
PACKAGE DIMENSIONS
PDIP−8
P SUFFIX
CASE 626−05
ISSUE N
14
58
b2
NOTE 8
D
b
L
A1
A
eB
E
A
TOP VIEW
C
SEATING
PLANE
0.010 CA
SIDE VIEW
END VIEW
END VIEW
WITH LEADS CONSTRAINED
DIM MIN MAX
INCHES
A−−−− 0.210
A1 0.015 −−−−
b0.014 0.022
C0.008 0.014
D0.355 0.400
D1 0.005 −−−−
e0.100 BSC
E0.300 0.325
M−−−− 10
−−− 5.33
0.38 −−−
0.35 0.56
0.20 0.36
9.02 10.16
0.13 −−−
2.54 BSC
7.62 8.26
−−− 10
MIN MAX
MILLIMETERS
NOTES:
1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M, 1994.
2. CONTROLLING DIMENSION: INCHES.
3. DIMENSIONS A, A1 AND L ARE MEASURED WITH THE PACK-
AGE SEATED IN JEDEC SEATING PLANE GAUGE GS−3.
4. DIMENSIONS D, D1 AND E1 DO NOT INCLUDE MOLD FLASH
OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS ARE NOT
TO EXCEED 0.10 INCH.
5. DIMENSION E IS MEASURED AT A POINT 0.015 BELOW DATUM
PLANE H WITH THE LEADS CONSTRAINED PERPENDICULAR
TO DATUM C.
6. DIMENSION E3 IS MEASURED AT THE LEAD TIPS WITH THE
LEADS UNCONSTRAINED.
7. DATUM PLANE H IS COINCIDENT WITH THE BOTTOM OF THE
LEADS, WHERE THE LEADS EXIT THE BODY.
8. PACKAGE CONTOUR IS OPTIONAL (ROUNDED OR SQUARE
CORNERS).
E1 0.240 0.280 6.10 7.11
b2
eB −−−− 0.430 −−− 10.92
0.060 TYP 1.52 TYP
E1
M
8X
c
D1
B
A2 0.115 0.195 2.92 4.95
L0.115 0.150 2.92 3.81
°°
H
NOTE 5
e
e/2 A2
NOTE 3
MBMNOTE 6
M
H’H H H ILHLILH , A Le @ L In
NCP1653, NCP1653A
www.onsemi.com
21
PACKAGE DIMENSIONS
SO−8
D SUFFIX
CASE 751−07
ISSUE AK
SEATING
PLANE
1
4
58
N
J
X 45_
K
NOTES:
1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSION A AND B DO NOT INCLUDE
MOLD PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.
5. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 (0.005) TOTAL
IN EXCESS OF THE D DIMENSION AT
MAXIMUM MATERIAL CONDITION.
6. 751−01 THRU 751−06 ARE OBSOLETE. NEW
STANDARD IS 751−07.
A
BS
D
H
C
0.10 (0.004)
DIM
A
MIN MAX MIN MAX
INCHES
4.80 5.00 0.189 0.197
MILLIMETERS
B3.80 4.00 0.150 0.157
C1.35 1.75 0.053 0.069
D0.33 0.51 0.013 0.020
G1.27 BSC 0.050 BSC
H0.10 0.25 0.004 0.010
J0.19 0.25 0.007 0.010
K0.40 1.27 0.016 0.050
M0 8 0 8
N0.25 0.50 0.010 0.020
S5.80 6.20 0.228 0.244
−X−
−Y−
G
M
Y
M
0.25 (0.010)
−Z−
Y
M
0.25 (0.010) ZSXS
M
____
1.52
0.060
7.0
0.275
0.6
0.024
1.270
0.050
4.0
0.155
ǒmm
inchesǓ
SCALE 6:1
*For additional information on our Pb−Free strategy and soldering
details, please download the ON Semiconductor Soldering and
Mounting Techniques Reference Manual, SOLDERRM/D.
SOLDERING FOOTPRINT*
ON Semiconductor and the are registered trademarks of Semiconductor Components Industries, LLC (SCILLC) or its subsidiaries in the United States and/or other countries.
SCILLC owns the rights to a number of patents, trademarks, copyrights, trade secrets, and other intellectual property. A listing of SCILLC’s product/patent coverage may be accessed
at www.onsemi.com/site/pdf/Patent−Marking.pdf. SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty,
representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product
or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in
SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must
be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products
are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or
for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products
for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against
all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended
or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action
Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
N. American Technical Support: 800−282−9855 Toll Free
USA/Canada
Europe, Middle East and Africa Technical Support:
Phone: 421 33 790 2910
Japan Customer Focus Center
Phone: 81−3−5817−1050
NCP1653/D
LITERATURE FULFILLMENT:
Literature Distribution Center for ON Semiconductor
P.O. Box 5163, Denver, Colorado 80217 USA
Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada
Fax: 303−675−2176 or 800−344−3867 Toll Free USA/Canada
Email: orderlit@onsemi.com
ON Semiconductor Website: www.onsemi.com
Order Literature: http://www.onsemi.com/orderlit
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